Op Amp with positive feedback (hysteresis) driving N-MOSFET oscillates

Question

I have a Supercap voltage control circuit that is based on a On Semiconductor NCS333 Op Amp that's configured with hysteresis (using positive feedback) that drives two N-MOSFETs - one that is actually discharging Supercap when voltage goes over some pre-defined limit (~2.5V in my case) and another one to indicate that discharging is active now.

I've used DMN1019U MOSFET to discharge the Supercap as it can tolerate up to 10.7A of current with a very low \$\mathrm{V_{GS(th)}}\$ and \$\mathrm{R_{DS(on)}}\$, so it won't overheat at high currents. Current through MOSFET is limited by 2512-case resistor, \$\mathrm{R_S}\$, so most heat would be generated by resistor and not MOSFET.

When I'm using any resistor down to ~1.8Ohm - system works fine and correct, but if I want to increase discharge current by placing two 2.2Ohm resistors in parallel resulting in 1.1Ohm total resistance (for example) - output of Op Amp starts to oscillate and MOSFET starts to act as a variable resistor and heats up very quickly as its resistance becomes higher than \$\mathrm{R_S}\$ one.

I have tried to use snubber circuit for Op Amp, it helped a little bit, I was able to reduce \$\mathrm{R_S}\$ to ~1.5Ohm but if I go lower - oscillation starts again.

Is there any way to stabilize this circuit? I know that DMN1019U has a very high gate capacitance of 2588pF @ 10V, but I need to choose a MOSFET with lowest available resistance and \$\mathrm{V_{GS(th)}}\$ so power dissipation would be occurring in \$\mathrm{R_S}\$ rather than MOSFET.

Answer 1

After a reading your question and having a quick look at the datasheets of the NCS333SN, I am sure that the problem is the heavy capacitive loading of the amplifier by the DMN1019. The two details motivate my belief

1. The "Dynamic performance" parameter table at p. 6 states in each entry (apart from the slew rate SR entry) a value \$C_L=100\mathrm{pF}\$ for the load capacitance. This suggests that it is not advisable to increase too much beyond that limit the load capacitance.
2. When you have a look at the "Typical characteristics" section, looking at figure 1, p. 7, you notice that the nice phase margin at \$f=f_T\$ of the amplifier is a more than respectable \$\phi_M\simeq 60^\circ\$ but again when the load capacitance is \$C_L=100\mathrm{pF}\$. And if look at figure 13, p. 9, you see that the small signal overshoot is over \$60\%\$ when \$C_L=1000\mathrm{pF}\$.

Since the typical gate capacitance of the DMN1019 is \$C_\mathrm{G}>2500\mathrm{pF}\$, we'll surely find troubles if we connect the OpAmp output directly to it: and even using a series gate resistor may not get you out of troubles, if this resistor is significantly lower respect to e.g. the standard load stated for the slew rate test, i.e. \$R_L=10\mathrm{k\Omega}\$, as you have noticed with your tests.

What could you do?

1. Since you use the MOSFET as a means for discharging a supercap when the voltage across it starts to rise above the safe \$2.5\mathrm{V}\$ level, you do not need to be particularly fast in turning it on. Therefore you could try to put a \$10\mathrm{k\Omega}\$ gate resistor and see if the amplifier remains stable.
2. Otherwise, if you desire to have nevertheless a quick response, you should try to find an optimal value for the gate resistor \$R_\mathrm{G}\$, by starting from \$R_\mathrm{G}=1000\Omega\$ and rising it until the circuit is stable for all desired resistor loads.

Final note

Following mkeith's comment above, I think is a very good idea to find a low voltage comparator and use it instead of the NCS333: despite their circuit topology can be (also very) similar, OpAmps and comparators cannot be used interchangeably without any care. Just to give some examples, devices like TLV3691 or NCS2200 could be a nice choice.

Answer 2

One guess: There's a feedback path which should be blocked. Replace R8 with two 2,2 kOhm resistors in series and connect a capacitor, say 10uF between the joint and the GND. Also a cap simply placed over the reference IC can work.

Another guess: Your circuit is built on a breadboard and it's full of unwanted parasitic parts.

Answer 3

The NCS333 cannot operate well as a comparator at 2.5V with an insufficient swing to get the rated RdsOn. Thus at high RdsOn, and low loads the hysteresis reduces to the point where you have almost none.

Put a level shifter or inverter to get a full swing on the output and swap inputs or try more hysteresis.

You should at least pay more attention to the output swing specs on the Op Amp and Vgs vs RdsOn and use a better comparator instead of a precision Op Amp.

edit:

This is what concerned me about the gate drive voltage using this Op Amp as a low voltage comparator. p7 https://www.onsemi.com/pub/Collateral/NCS333-D.PDF

Adding a large gate resistor will help decouple reactance effects with positive feedback that you have being reduced by the output swing. The table implies a rail to rail CMOS swing output with 50mV rail offset, while the curves imply the output swing is far from Rail to Rail yet Vdd, Vss implied it is still CMOS.

After starting at it for a while, I saw the error in my interpretation now. Where the graph says Vs=5.5 meaning supply, they are using bipolar supplies here, but only define it as Vdd-Vss=Vs, so the graphs all start with a 50% swing.

Conclusion

My corrected analysis indicates you have excess gain at the resonant frequency due to 3rd order effects reducing phase margin and AC hysteresis with the load R load and C of supercap approaching the open-loop pole of the Op Amp., which may be corrected by suitable compensation.

There are 3rd order effects with RC capacitances in 3 parts (IC, FET-Ciss, Supercap) each add a pole and reducing load R pushes the pole up near the IC open-loop breakpoint.

Non-linear effects of IC: Hysteresis results in zero gain, yet the IC open loop has 130dB typ gain with a breakpoint well below 10Hz. With 10F and 1.1 Ohms, that's a bit higher.

Recommendations

The improve your stability, you can add phase-lead RC compensation or switch to a bipolar comparator or decouple the gate Ciss with a large series resistor to lower the gain at the resonant frequency with Ciss using say 10k ohm.