I went through many textbooks and websites and I found out the derivation for AC resistance for diode which is \$r_d=26mV/I_{F}\$ where as for ac emitter resistance it is \$r_e=25mV/I_E\$ for which I didn't get any derivation or explanation. So, I wanted to request the forum for mathematical derivation or are they same with a valid reasons.


It's just a linearization of the Shockley equation. The large signal model for a diode is:

$$I_F=I_S\cdot\left(e^{\cfrac{V_F}{n k T/q}}-1\right)~~~~~~~~~~~~~(1)$$

\$n\$ is the emission coefficient and is by default set to 1. In many small signal BJTs, the default is fairly accurate. With many diodes, it's not, and is usually larger -- not unlikely from 1.6 to 3 or more. But in the two cases you mentioned, I'm pretty sure it was taken as the default value.

The value of \$\frac{k T}{q}\$ is a matter of basic physics and ambient temperature. It's called the thermal voltage and is, at room temperatures, somewhere from \$25-26\:\textrm{mV}\$.

\$I_S\$ is known as the saturation current and for BJTs is typically in the area of \$2\times 10^{-14}\:\textrm{A}\$ for discrete, small signal BJTs. For discrete diodes, it's usually more, often by a factor of 1000 or more.

Linearization of the above equation is pretty easy:

$$\begin{align*} D\left(I_F\right)&=D\left(I_S\cdot\left(e^{\cfrac{V_F}{n k T/q}}-1\right)\right) \\ \\ \textrm{d} I_F&=I_s\cdot D\left(e^{\cfrac{V_F}{n k T/q}}-1\right) \\ \\ \textrm{d} I_F&=I_s\cdot e^{\cfrac{V_F}{n k T/q}} \cdot D\left(\cfrac{V_F}{n k T/q}\right) \\ \\ \textrm{d} I_F&=I_s\cdot e^{\cfrac{V_F}{n k T/q}} \cdot \cfrac{\textrm{d} V_F}{n k T/q}~~~~~~~~(2) \end{align*}$$

At this point, it is helpful to recall equation (1) above and note that the "-1" term is negligible in almost all cases. So we can substitute \$I_F\$ into equation (2) above, giving:

$$\begin{align*} \textrm{d} I_F&=I_F \cdot \cfrac{\textrm{d} V_F}{n k T/q}~~~~~~~~~~~~~~~~~~~~~~~~~~(3) \end{align*}$$

Trivial algebra now yields:

$$\begin{align*} \frac{\textrm{d} V_F}{\textrm{d}I_F} &= \frac{n k T}{q I_F} ~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~(4) \end{align*}$$

Since \$n=1\$ and thus \$\tfrac{n k T}{q}\approx 26\:\textrm{mV}\$ at room temperature, equation (4) reduces to the equation you've been seeing. Whether it is 25 or 26, is rarely important. (It might be if you are using this equation to measure the ambient temperature or if you are struggling with circuits that otherwise depend upon this parameter's exact value in exact circumstances.)

In the case of the BJT, the usual much simplified active region equation is:

$$I_C=I_S\cdot\left(e^{\cfrac{V_{BE}}{n k T/q}}-1\right)~~~~~~~~~~~~~(5)$$

But a similar derivation occurs. And since the emitter collects both the base and collector currents, which travel across that PN junction, the use of \$I_E\$ rather than \$I_C\$ is appropriate. But those two values are usually so similar, you may find either form used, in practical applications.

In the case of a small signal BJT, I'd be more likely to use the equation since it more usually applies (ignorant of better specifications.) In the case of diodes, excepting diode connected BJTs, I'd usually be suspicious of it as the emission coefficients are usually not 1, but larger.

Oh. Keep in mind that the thermal voltage is in millivolts. An emitter current of \$1\:\textrm{mA}\$ suggests \$re \approx 26\:\Omega\$. You need to keep your multipliers straight. (When you see \$\tfrac{26}{I_E}\$, then you must either read the 26 as being millivolts with \$I_E\$ being in amps, or else you must read the \$I_E\$ as being specified in milliamps.)

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  • \$\begingroup\$ so why is bulk size of a diode not in the equation which obvious affects \$V_{ce}/I_e\$ at the same current when saturated or \$\Delta V_e/\Delta I_e\$ when tested for this impedance and does not include hFE when know that is factor as well as base impedance. \$\endgroup\$ – Tony Stewart Sunnyskyguy EE75 Nov 5 '16 at 8:29
  • \$\begingroup\$ Bulk size of the diode will affect capacitance, but isn't in the Ebers-Moll model. The base spreading resistance and beta are also not part of the model (and usually very minor in effect). \$\endgroup\$ – Whit3rd Nov 5 '16 at 21:37

"*....where as for ac emitter resistance it is \$r'e=25/I_E\$ "

From jonk`s excellent explanation - and in conjunction with the above quoted sentence - we can derive a very important property of the quantity r'e. The TRANSCONDUCTANCE of a BJT is (with sufficient accuracy)

$$\frac{dV_{be}}{dI_c} = g_m = \frac{I_c}{V_T} (\text{with } V_T \sim 26 mV)$$

Note that we have \$g_m = 1/r_e'\$.

The transconductance \$g_m\$ plays the major role for finding the voltage gain of a transistor stage; \$g_m\$ can be calculated also using the small-signal parameters \$\beta = \frac{dI_c}{dI_b}\$ and \$r_{\pi} = \frac{dV_{be}}{dI_b}\$ as \$ g_m = \frac{\beta}{r_{\pi}} \$.

However, for practical design purposes, who knows the values for \$\beta\$ and \$r_{\pi}\$? Therefore, it is common practice to use \$g_m = \frac{I_c}{V_T}\$ because our design starts always selecting a proper \$I_c\$ value.

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